Waveguide hybrid junctions



March 20, 1956 RlBLET 2,739,287

WAVEGUIDE HYBRID JUNCTIONS Filed March 17, 1950 2 Sheets-Sheet l INVENTOR. Henry J fl/b/e! March 1956 H. J RIBLET WAVEGUIDE HYBRID JUNCTIONS 2 Sheets-Sheet 2 Filed March 17, 1950 1%. 1|] a. 5917712781770 Mode Ref/e c/ed F//d mine. 26 2b Figmf. //a

INVENTOR. Henry J Rib/9f BY J a Z WAVEGUIDE HYBRID JUN CTIONS Henry I. Riblet, Wellcsley, Mass.

Application March 17, 1950, Serial No. 150,131

7 Claims. (Cl. 333-11) This invention relates to waveguide hybrids as defined by W. A. Tyrrell in the P. I. R. E. November 1947, p. 1295.

A waveguide hybrid as defined by Tyrrell is a waveguide circuit, having four (two input and two output) waveguide terminals, which has the property that energy incident on one of the input terminals will divide evenly between the two output terminals with only a small fraction of the energy escaping through the other input terminal. in general, the less energy escaping out of the other input terminal, that is the greater the isolation between the two input terminals, assuming matched terminations on the output terminals of course, the better the hybrid. Similarly, the evener the power division at the output terminals, the better the hybrid. Needless to say no hybrid is ever perfect in either of these characteristics.

For the purposes of this specification, I shall restrict the term hybrid to four terminal waveguide networks for which the power divisions is equal within a tolerance of 3 decibels and for which the power out of the otherinput terminal is decibels less than the power incident on the first input terminal.

This invention relates to parallel guide hybrids having, for many applications, a useful configuration of terminals, and parallel guide hybrids which maintain their electrical characteristics over wide bands of frequency and are capable of handling high power without breakdown.

This invention further discloses specific embodiments wherein a waveguide hybrid employs a pair of substantially parallel rectangular waveguides, hence the name, having one of their narrow walls in common, said wall being apertured by a single hole which extends substantially the full height of the narrow common wall of the waveguide and which has a length approximately one free space wavelength at the mean operating frequency. The aperture in the common wall makes it possible for the section of the two parallel waveguides in its immediate vicinity to support the lowest TEm mode associated with a waveguide having twice the width of the original waveguides. (For diagrams of field configurations of the TEio and TEzo modes reference is made to Schellkunoff Electromagnetic Waves p. 395.) Signals in each waveguide which travel down the waveguides through the apertured section will be unaficcted by the apertured common wall if the signals are of the same magnitude and are out of phase. if the signals are in phase, however, said signals upon reaching the apertured section will behave as a common signal in a single double width waveguide.

In the waveguide of doubl width, the phase velocity of a lowest mode TEiu wave is substantially less than that in the original waveguides. Now a signal incident only on one waveguide can be resolved into identical inphase and out-of-phase components in the two waveguides. In the apertured section, the phase of the in phase component will advance more rapidly than the phase of the out-of-phase component, causing a resultant change in the vector sum of the signals in each guide and consequently a change in the relative power levels in Patented Mar. 29, 1956 2, the two guides. Thus by varying the length of the apertured section and hence the degree of phase dilference between the in-phase and out-of-phase components, the amount of power transformed from one guide to the other may be regulated.

In addition, if the reflections back to the inputs to the guides for both the in-phase and out-of-phase components of a signal incident on only one guide happen to cancel out, then no energy will be reflected out of either input. Since the out-of-phase components are not affected by the aperture in the common wall, we have only to arrange it so that the reflection, for the in-phase components, from the front end of the aperture cancels out the reflections from the back end of the aperture in order that none of the signal incident on one of the input guides be sent out the other input waveguide.

My invention depends on my discovery that suitable dimensions for the apertured section may be chosen so that the condition for equal power division and the condition for high isolation between the input terminals can be satisfied simultaneously. Moreover these dimensions can be chosen so that the two conditions are satisfied simultaneously over wide ranges of frequency. Moreover the dimensions can be chosen so that the two conditions are satisfied simultaneously over wide ranges of frequency with a resulting hybrid structure which will handle high power levels without breakdown. The important dimensions of the apertured sections are its width, its height, its length and the amount of capacitive loading placed in the aperture. As will be pointed out in greater detail the width and height of the apertured section must be chosen so that only the first, TEID and second T1520 modes are capable of propagating in the apertured section. its length must be chosen so as to obtain the approximately desired power balance and then the capacitive loading selected to give the desired power balance simultaneously with the required high order of isolation between the input terminals.

Since these hybrids are inherently broad band devices it follows that their performance as hybrids is not critically determined by their dimensions and hence it is im possible to give sharply defined limits on the dimensions of the structure.

The invention may be more clearly understood by reference to the accompanying drawing, wherein Figure 1 gives a cutaway view of a preferred embodiment of my invention. Figure 2 is another embodiment of my invention illustrating among other things how it may be bent in the E plane. Figures 3, 4, and 5 show alternate arrangements of the central wall of the hybrid which are capable of giving essentially the same performance as obtainable with the structure shown in Figures 1 and 2. Figures 6 and 7 show alternate configurations at the outer walls of the hybrid which are equivalent to that shown in Figure 1. Figures 8, 9, and 10al0f are schematic drawings to be used in explaining the operation of my invention.

Similar numerals refer to similar several views, in which:

The numeral 1 designates a waveguide hybrid composed of two waveguides 2a and 2b symmetrically joined along their common narrow walls 3. An aperture 5 is formed between waveguides 2a and 212 by removing substantially all of the common wall for a distance of approxb mately one free-space wavelength. The ends of the aperture are denoted by So. The center of this aperture 5 is provided with wavelength-reducing capacitive projections 6 which consist of flat rounded domes projecting into the central portions of the hybrid l. The gap 6m is the minimum spacing between them. The outside walls 7 of the hybrid 1 are provided with wavelength-increas ing, inductive indentations 8 which parallel the aperture parts throughout the as shown in. Figure 1. This indentation begins at 82 and. sshss ts. HQIIQWQ F. saint. at 8m,

Figure 2 is an alternate arrangement of my hybrid differing from that of Figure l in that waveguides 2a andZb. are nolonger straight but arebent in their E plane. Flat projections 6 have been replaced by thin fins 6a. In forming coupling aperture 5; a small amount of the common wall 3. has been retained as shown at 9. It will also be noticed no indentation has been provided in the outer walls 7 of hybrid 1'.

In Figure. 3, the coupling aperture 5 in the common wall 3 is provided with a plurality of metallic posts 6 of a capacitive. nature. They project from only one wall, however. In Figure/t tapered plates 60 add a distributed capacity to the coupling aperture 5. In Figure 5, the capacity is provided in the coupling aperture 5 by a dielectric slab 6d. As will be pointed out later in the specifications, the important characteristic which the several. forms of capacitive loading 66d have in common is their ability to shorten the wavelength of the fundamental made propagating in the coupling section 4 For this reason they will be collectively referred to as wavelength reducing means.

In Figure 6 the indentations 8 of the outer walls 7 of the hybrid 1 are replaced by a series of closely spaced inductive posts 8a. In Figure 7, the indentation 8b is straight instead. of being tapered like the indentations 8 of Figure 1. It will be pointed out later that the characteristics which the several forms of inductive loading 88b have in common is their ability to increase the wavelength of the second mode, TEzo propagating in the coupling section. For this reason these structures will be referred to as wavelength increasing means. It is further to be noticed that no capacitive loading is shown in the coupling apertures 5 of Figures 6 and 7.

For convenience in writing the specification and the claims to follow the following terms and symbols are specifically defined:

l. Coupling aperIure.-The aperture 5 cut in the common wall 3 will be called the coupling aperture.

2. A pertured section.The portion of the hybrid 1, containing the coupling aperture 5, which is capable of supporting the T510 as well as the T1320 modes will be called the apertured section of thehybrid.

3. The length L of the apertured section 4 is the distance between the ends 5a of the coupling aperture.

4. The height H of the apertured section is the maximum distance between the top and bottom wide surfaces of the apertured section.

5. The median width Wm of the apertured section is the distance between the side (narrow) walls of the, apertured section measured perpendicular to the common narrow wall 3 at the center of the coupling aperture.

6. The terminal width Wt of the apertured section is the distance between the side (narrow) walls of the apertured section measured perpendicular to the common narrow wall 3 at the ends 5a of the coupling aperture.

7. The gap spacing Sg is the minimum distance measured between the capacitive projections 6. In a case such as Figure 3, it will be the minimum distance from the capacitive projection to the opposite wall of the apertured section.

8. The indentation length Li isthe distance measured along the length of the apertured section between the beginning and end 8e of the inductive loading 8 at the side walls of the hybrid.

In explaining the nature and operation of my invention reference is made to Figures 8 and Illa-f. For the general purpose of explanation, it is convenient to picture the apertured section as consisting of two identical parallel waveguides with a length of the common wall removed as shown in Figurestl and 9 Of course, all of the remarks to follow may be readily extended to any of the hybrids hsw i n. h's r i re Figure 8 gives a ema c e of h is ut e of the electric field in two waveguides when symmetrical fislsisare ncident. on nput. penings .04:. and. 1.01mi waveguides 2a and 212. As shown in Figure 8, the field configuration will always be symmetrical about the center wall 3 so long as the hybrid 1 is mechanically symmetrical about this Wall. It will be important in the explanation to follow to note especially that only symmetrical modes may be excited in the apeptured section 4 of the hybrid 1 containing the aperture 5. As shown at section B-B in Figure 8 this mode is the T1310 or lowest mode which may propagate in a waveguidehavingthis width, it having been discovered that the next symmetric mode TEsc must not be. allowed. to. propagate in the aperturedsection 4. For the frequencies and waveguide sizes in common use this requires some means of filtering out this mode in the apertured section. This is accomplished in the preferred embodiment of this invention by the indentations 8 provided in the outer walls 7 for length of the apertured section 4, as shown in Figure 1. These indentations reduce the width of the apertured section to less than 3/2? where A is the free space wavelength of the highest operating frequency of the hybrid. As is well known to the art this effectively suppresses the TEsp mode. For some frequencies and guide sizes, as shown in Figure 2, indentations and the like are not required, the guide width itself beingsuch that theTEso mode will not propagate in the apertured section. Of course, any other wave length reducing means as for example a series of inductive posts 8a as shown in Figure 6 would have the same effect.

Figure 9 gives a schematic View of the distribution of the electric field in the two waveguides when antisymmetrical fields are incident on openings 10a and 10b of- Waveguides 2a and- 211. As is shown in Figure 9, the field configuration will always be antisymmetrical about the center wall 3 so long as the hybrid 1 is mechanically symmetrical about it and the excitation is antisymmetric. Thus the only mode which can be excited in the coupling section 4 unde r these conditions is the second TEzo, mode as is shown at section E-E in Figure 9. In particular the electric field in the connecting aperture 5 will be zero for this mode. Accordingly the capacitive loading 6 shown in my invention will have very little elfect on this mode in the apertured section. Whenpower is incident on the guide 2b at input terminal 1012, it proceeds along that waveguide until it encounters the aperturedsectionl Here it begins to cross over into the other waveguide 2p. Under suitable conditions, by the time the energy reaches the end oi the apertured section, it will have divided so that the power leaving at output terminal 11a just equals that leaving at output terminal 11b. If in additiorrno power leaves at input terminal 101: and none is reflected at input terminal 1%, assuming perfectly matched terminations at 11a and 11b, the structure is an ideal wave. guide hybrid as previously defined. The basic conditions which the apertured section must satisfy in order that hybrid performance be realized can now be deduced.

Under the usual test conditions, energy is incident on a single input terminal of the hybrid, say terminal 10b; As is well "known to the art (see Kyle Technique Jot Microwave Measurements, Radiation Laboratory Series, volume'll, pp. 889) this situation may be obtained by the; superposition of the two field configurations of Figures 8 and 9 ifwe assume that the incident voltages are given in magnitude and phase by the rotating vectors shownin Figures llla and 10b. As we have seen, the symmetry and antisymmetry of these two modes is maintained in the apertured section. Accordingly the reflected and trans,- mitted voltages in each mode will preserve the symmetry or antisymmetry of the incident voltages. This is shown for the reflected fieldin Figures and 10d and for the transmitted fieldinFigures 102 and 10f. Of course, the phases and, amplitudes of the. reflected and transmitted qltasss, e ative. to a h. he d. hsn i n z q t: ages willbe determined. by,the. geometry of; the hybridun rnss 'nisl ratioa We e mm d a l that. the @0111 dition for complete isolation between input terminals a and 10 is that the reflected voltages in both modes shall add up to zero at terminal 10a. A similar condition holds at terminal 10* in order that the input S. W. R. shall be unity. If both conditions are to be satisfied, we readily conclude from Figures 100 and 10d that the reflected voltages in the symmetric and antisymmetric modes must both be zero. This we shall call Condition 1 for an ideal parallel guide hybrid. For the hybrids of my invention this condition is satisfied approximately for the antisymmetric mode as we have already seen. Thus the principal effect of Condition 1 is to require that the apertured section be matched for the incident symmetric voltages of Figure 8.

Under the assumption that Condition 1 has been perfectly fulfilled, we see that the voltages shown in Figures 10c and 10 of the transmitted field in both modes are of exactly the same magnitude. Thus the manner in which the power is shared between the outputs is determined entirely by the phase relationships between these voltages at the output terminals 11a and 1112. Of course until the apertured section is reached, there will be no relative phase shift and, of course, no power transferred into guide 2a. The guide wavelength for the symmetric TEio mode will be less than the guide Wavelength in the antisymmetric TEzo mode in the apertured section and, of course, the relative phases will differ as a consequence. Once the apertured section has been passed, the relative phases of the two modes are fixed and there is no possibility for further power transfer. This picture gives us two intersecting consequences. in the first place, simple addition of the voltages of the transmitted fields of Figures 106 and 10] for arbitrary phases will show that the output voltages of the hybrid (on the assumption of unity standing wave ratio and infinite isolation) must always be ninety degrees out of phase. Moreover, if the device is to behave as a hybrid, the transmitted fields in the two modes must themselves differ by ninety degrees. Thus if Condition 1 is satisfied by a device as shown in Figures 1-9, Condition 2 for hybrid performance is that the length of the apertured section measured in electrical degrees for the symmetrical, TEiu mode must exceed its electric length as measured for the antisymmetric TE mode by ninety degrees.

The number of electrical degrees of phase shift for the antisymmetric mode in traversing the coupling section is approximately given by L/Aa, where L is the length of the apertured section as previously defined and M denotes the guide wavelength of the antisymmetric TE20 mode in the apertured section. The number of electrical degrees of phase shift for the symmetrical TEm mode in transversing the apertured section is complicated by the reflections which take place at the ends 5a of the coupling aperture 5 and at the capacitive loads 6. If we denote the resulting phase shifts at these discontinuities by gDe and Q04: respectively we have for the total phase shift in the apertured section for the symmetric mode Lks-I-goe-I-r c where 1\s represents the guide wavelength in the apertured section for the symmetric TEro mode. Thus Condition 2 for hybrid performance can be expressed I have discovered the following facts in regard to the dimensions of the elements of the apertured section which are important in constructing hybrids as pictured in Figures 1-7. They are:

l. The reflections in the symmetric TEm mode at the ends 5a of the coupling aperture 5 are minimized by having the aperture 5 extend the full height of the guide at its ends 5a as shown for example in Figure 3.

2. The impedance at the end 5a of the aperture 5 as seen from the apertured section 4 in the symmetric TEIO mode is essentially an inductive susceptance that increases with decreasing wavelength, and decreasing terminal width Wt: of the apertured section measured at its end points 5a as previously defined.

3. The length of the apertured section required falls in the range, \mm.1.25 \max. where 7min. and Amex. are the minimum and maximum operating wavelengths respectively.

4. The terminal width We of the coupling section in the vicinity of the ends of the aperture must be less than A of the free space wavelength at the highest operating frequency.

5. (pa and gac are increasing functions of frequency whereas is a decreasing function of frequency.

6. Increasing the amount of the capacitive loading 6 increases the frequency at which maximum isolation is realized and increases the power transfer through aperture.

7. The gap spacing Sg is always greater than %H where H has been defined as the height of the apertured section.

8. The point of minimum spacing between the capacitive loads should be located at or near the center of the aperture.

With this information one skilled in the art would have no difiiculty in constructing" a hybrid by following the following steps:

Construct a trial apertured section in which the coupling aperture has a length less than at the maximum operating frequency. irovide a capacitive structure in the aperture which crosses the guide except for a gap which does not exceed one fourth the height of the guide. Measurements of the performance of the device and a review of the above experimental results will allow one to quickly determine the proper gap size and aperture length for hybrid performance. For example, reducing the size of the gap reduces the capacity, thus t e and accordingly less power is transferred to output 1115. Increasing the length of the coupling aperture, by a similar argument, increases the power transfer. it will now be observed, however, that the frequency of perfect isolation has been raised. Proceeding thus, one can satisfy Conditions 1 and 2 at the same time.

For example I have constructed, among others, hybrids whose internal dimensions fall within the given tolerances as follows:

All of these hybrids had apertured sections Whose heights were .400. Measurements were centered at 3.3 centimeters and hybrid performance was obtained over bandwidths considerably in excess of 12%.

As will be clear to one skilled in the art, the height of the apertured section is immaterial to the performance of these hybrids as long as the capacitive loading does not excite any mode other than the TEio and TEao modes. Clearly apertured sections of greater height can be used if the capacitive obstructions are symmetrically placed on the top and bottom of the apertured section than for asymmetrical loading. As hydrid 4 shows, however, the capacitive projection may project from only one side.

Although hybrids constructed in accordance with the shots rqsedu e ope at ery. at s actcr lyt it ha b en foundt at certain additional precautions tendto improve the h br d cha acter s ic ver, a pec f ed. ba d w t in the first place the Ilia mode must not be allowed to. propa a e... n. h ener ure sect on. Th s requir s a Wt and Wm for the apertured section shall be lessthau 3 he e A t e e same wave e th. at he g e t eaet tins f equentur he more t min miz r fle tion t t e. e s, o t accurate r he I ia mo e. the terminal width, Wt, of the apertured section must be mewhet e te han he. f ee. same wavelength at t lowest operating frequency. l'have also learned that the aperture must extend at least 75% of the full height of the guide at its extremities,

The basis for broad bandpower division characteristics rests on my discovery, that the-re exist: dimensions, within; thqtolerances given so that Condition 2, is satisfied: over widebands of frequency. This, depends on the fact that there exist value-sot L, and (Po sothat the ipcreasingfrequency characteristics of (pa and 00 are just balanced, by the decreasing. frequency ehanactenistic of,

(Li. a M i The basis for the broad band isolation and S W. cha ac er t rade On; m d ssn ew ha apac se nss m be e e mine Whishm tq o t. e eli stions from the ends of the apertures over wide bands of frequency. This possibility may be'attributed, to the compensating phase and magnitude characteristics of the reflection from the ends of the apertureras seen from its, center.

To obtain a broad band hybridthen one has only to start with, an apertured section for Which the above conditions are satisfied by the coupling aperture and apertured section and proceed as before to obtain hybrid performance at the center of the desiredfrequency band, Comparison of the performance over the required band. of several hybrids obtained in this way starting withdifferent width aperture sections will readily allow the designer to obtain a hybrid whose characteristics are broad band.

1 have also discovered that small. improvements in performance are obtained by a gradual pinching inof the outer wall of the coupling sectionas shown at 8111 in Figure l and by properlychoosing the distance L1 between the ends lie of the inductive loading 8 of Figure 8.

For example i have constructed hybrids of the type pictured in Figure l in which L=l.205", Wr=l.775, Wm:i-.7l0- and the spacing between the tips of flat /2" diameter domes is 70% of H for; which the power balance out terminals 11a and 11b isequal to within, :2 (1b, the isolation between inputs 19a and b is in excess 01130 db, andfor which the S. W. R., l.05 over the frequency band from 85Q0to 9600 me. For this. performance L 1.500".

It iskuown that many variationsin the dimenions of; the coupling section may be made without seriously impairing the performance characteristics. of these hybrids. For example, complete end for end symmetry is not essential nor must the capacitive projections be;placed eX- actly in the coupling aperture. These changes however, do not depart from the spirit of this invention.

Having now described my invention I claim:

1. A hybrid junction operative over a relatively broad microwave spectrum centered at a predetermined midbandfrequency comprising, a hollow rectangular conductive structure having substantially parallel broad and narrow walls, a conductive plane partition extending 1ongitudinally and centrally through said structure coextensively with and parallel to said narrow walls, said partition thereby dividing said structure into first and second like rectangular, waveguides having, a. common narrow wall each dimensioned for normalpropagation oflmicrowave energy only in the TzEzm made over said mic wave spectrum. aid P rt t b ing f ed h a lengthwise apert re of substantially rectangular crossseqtiqu up ng i firs nd se ond av g des d fining an. apertured section having a. width equal to that of; said broadwal s Qf: S idconductive structure and being thereby capable, of propagating microwavev energy in both T.E .1,u and, 113.2,) modes over said microwave spectrum, said. apfilf re having a height atthe ends. thereof substantially equal to the height of said narrow walls, and centrally. disposed means for capacitively loading saidaperture, said aperture length and, capacitive. loading being, mutual y arranged. whereby for all frequencies throughout said-,rnicrowaVeSPec Ium,. the electrical. length of said apertured section, for said T.E.1,p. mode. is substantially ninety degree Siiatcr than. the. electrical length, thereof for said, T.E.2,o mode and further, whereby substantially no-. microwave, energy is. reflected, by said, apertured section, iucl uding said, ends. of said aperture and said. capacitive. loading, means, in, the transmission, ofi microwave energy therethrough in said T.E.1,oand T.E.2,o modes throughout said. spectrum 2. Apparatus; as in. claim 1 wherein said-,means for capacitively loading said, aperture comprises, apair of aligned. conductive dome-like elements-formed as integral' extensions of said broad walls. and extending inwardly toward, each other.

3. Apparatus-rein claim 1 wherein said centrally, dis: posed means for-capacitively loading said aperture comprises, a series; of dependent projections, extending from one of said: broad; walls, and substantially aligned: with said conductive partition.

4. Apparatusas-in claim 1; wherein said; centrally disf posed means-for capacitively loading; said aperture comprises, a pain of inwardlyextending curved elements disposed; substantially; in the. plane of said conductive partition and having; a minimum spacingsubstantially midway between the-ends of said aperture.

5 Apparatus as in claim 1 wherein said centrally disposed means for capacitively loading said aperture comprises,a dielectric structure disposed substantially in alignmentwith said;conductive partition and substantially mid way betweentheends of 'saidapert ure.

6. A hybrid junction operative over a relatively broadmicrowavespectrum centered at a predetermined midbandffrequency comprising, a hollow rectangular conductivestructure havingsubstantially parallel broad and narrowwalls; a conductive plane partition extending 1ongitudinally andcentrally through said structure coexten' sively with and'parallel'to saidnarrow Walls, said partition thereby dividing said structure intofirst and secondj likerectangularwaveguides having a common narrow wall each dimensioned for normal propagation of mi: crowave energy only in the T.E'.1,o mode over said microwave spectrum, said partition being formed" with a lengthwise aperture of? substantially rectangular crosssection coupling said first-and second waveguides defining an apertured section having a width equal to that of said-broad walls of saidconductive structure and being thereby capable of propagating microwave energy in both T.E.1,o and T.E.2,o modes over, said microwave spectrum, said aperture having aheightatthe ends thereof substantially equal to the height of said narrow walls, and centrally disposed 'means for: capacitively. loading'said .aperture, v said, aperture, length. and, capacitive loading, being, mutually arranged whereby for. all frequencies throughout said microwave spectrum, the combined electrical phase shifts forsaid 1T.. E.1,o.mode representedtby. the sum ofthe, electricallength of, said apertured section for saidv TiEim mode, the. phase shift introduced bysaid ends :of

said aperture and the phaseshiftintroduced bysaidicapaeitiveloading. meansall measured in electrical degrees, is, ninety, degrees tgreatenthan 1116361tri61 length; of,-sa.id apertured section measured, incleetrical degrees; for

said T.E.;,-o rnode, and. .further, whereby substantially no microwave energy is reflected by said apertured section, including said ends of said aperture and said capacitive loading means, in the transmission of microwave energy through said apertured section in either or both said T.E.1,n and T.E.2,o modes throughout said spectrum.

7. A hybrid junction operative over a relatively broad microwave spectrum centered at a predetermined midband frequency comprising, a hollow rectangular conductive structure having substantially parallel broad and narrow walls, a conductive plane partition extending longitudinally and centrally through said structure coexensively with and parallel to said narrow walls, said partition thereby dividing said structure into first and second like rectangular waveguides having a common narrow wall each dimensioned for normal propagation of microwave energy only in the T.E.1,o mode while being incapable of supporting propagation in the T.E.2,o mode over said microwave spectrum, said partition being formed with a lengthwise aperture of substantially rectangular cross-section coupling said first and second waveguides defining an apertured section having a width equal to that of said broad walls of said conductive structure and being thereby capable of propagating microwave energy in both T.E.1,o and T.E.2,0 modes over said microwave spectrum, said aperture having a height at the ends thereof substantially equal to the height of said narrow walls and a length lying between 0.75 free space wavelength for the lowest frequency of said spectrum and 1.25 free space wavelength for the highest frequency of said spectrum, the frequency width of said spectrum being of the order of fifteen percent of said midband frequency, and conductive means centrally disposed in said apertured section and conductively afiixed to at least one of said broad walls and extending into and thereby narrowing and capacitively loading said aperture, the narrowest portion of said aperture as measured at said conductive means being greater than one-quarter the height of and less than the full height of said ends of said aperture, the ratio of the length of said aperture measured between said ends thereof and the width of said apertured section lying between the limits of 0.55 and 0.75, said apertured length and capacitive loading being mutually arranged whereby for all frequencies throughout said microwave spectrum, the electrical length of said apertured section for said T.E.1,o mode is substantially ninety degrees greater than the electrical length thereof for said T.E.2,0 mode and further, whereby substantially no microwave energy is reflected by said apertured section, including said ends of said aperture and said capacitive loading means, in the transmission of microwave energy therethrough in said T.E.1,o and T.E.2,o modes throughout said spectrum.

References Cited in the file of this patent UNITED STATES PATENTS 2,407,069 Fiske Sept. 3, 1946 2,432,093 Fox Dec. 9, 1947 2,532,317 Lundstrom Dec. 5, 1950 2,543,425 Strandberg Feb. 27, 1951 2,558,385 Purcell June 26, 1951 2,573,746 Watson Nov. 6, 1951 2,607,850 Fox Aug. 19, 1952 2,615,982 Zaslavsky Oct. 28, 1952 OTHER REFERENCES Surdin: Directive Couplers in Wave Guides, The Journal of the I. E. E. (British), vol. 93, Pt. IIIA, No. 4, published 1946, pages 735 and 736 relied on. (Copy in Div. 69.)

The Journal of the Institution of Electrical Engineers, vol. 93, Part IIIA. (Radiolocation), No. 4, published in 1946 by The Institution, Savoy Place Victoria Embankment, London, W. C. 2 (using page 735 and 736). (Copy in Patent Oflice Library.) 

